OPERATIONAL AMPLIFIERS
Why do we study them at this point???
1. OpAmps are very useful electronic components
2. We have already the tools to analyze practical circuits using OpAmps
3. The linear models for OpAmps include dependent sources
TYPICAL DEVICE USING OP-AMPS
OP-AMP ASSEMBLED ON PRINTED CIRCUIT BOARD APEX PA03
PIN OUT FOR LM324
DIMENSIONAL DIAGRAM LM 324 LM324 DIP
LMC6294
MAX4240
CIRCUIT SYMBOL FOR AN OP-AMP SHOWING POWER SUPPLIES
LINEAR MODEL OUTPUT RESISTANCE
INPUT RESISTANCE
GAIN
7 5
12 5
10 10
:
50 1
:
10 10
:
−
Ω
− Ω
Ω
− Ω A
R R
O i
TYPICAL VALUES
CIRCUIT WITH OPERATIONAL AMPLIFIER
DRIVING CIRCUIT
LOAD OP-AMP
TRANSFER PLOTS FOR SOME COMERCIAL OP-AMPS
SATURATION REGION
LINEAR REGION
IDENTIFY SATURATION REGIONS OP-AMP IN SATURATION
CIRCUIT AND MODEL FOR UNITY GAIN BUFFER
= 0 +
+ +
− V
sR
iI R
OI A
OV
in: KVL
= 0 +
+ R
OI A
OV
inV
out- : KVL
I R V
in=
i: VARIABLE G
CONTROLLIN
i O O
s i out
R A R
V R V
+ +
= 1
1 SOLVING
→ 1
⇒
∞
→
S out
O
V
A V
WHY UNIT GAIN BUFFER?
BUFFER GAIN PERFORMANCE OF REAL OP-AMPS
Op-Amp BUFFER GAIN LM324 0.99999 LMC6492 0.9998 MAX4240 0.99995
⇒
∞
= A
) (
0 ⇒ =
+−
−= v A v v
R
O OTHE IDEAL OP-AMP
⇒
∞
i
= R
∞
=
∞
=
=
⇒ R
O0 , R
i, A IDEAL
i
+i
−THE UNITY GAIN BUFFER – IDEAL OP-AMP ASSUMPTION
v
sv
+=
+
−
= v v
v
OUT= v
−OUT S
v = v
v
OUT+
−
1
OUT
S
v
⇒ v =
USING LINEAR (NON-IDEAL) OP-AMP MODEL WE OBTAINED
1 1
out s i
O O i
V V R
R A R
=
+ +
PERFORMANCE OF REAL OP-AMPS Op-Amp BUFFER GAIN LM324 0.99999 LMC6492 0.9998 MAX4240 0.99995 IDEAL OP-AMP ASSUMPTION YIELDS EXCELLENT APPROXIMATION!
WHY USE THE VOLTAGE FOLLOWER OR UNITY GAIN BUFFER?
v
sv
+=
+
−
= v v
= v
−v
OS O
v v =
S
O
v
v =
THE VOLTAGE FOLLOWER ACTS AS BUFFER AMPLIFIER
THE SOURCE SUPPLIES POWER
THE SOURCE SUPPLIES NO POWER THE VOLTAGE FOLLOWER ISOLATES ONE CIRCUIT FROM ANOTHER
ESPECIALLY USEFUL IF THE SOURCE HAS VERY LITTLE POWER
CONNECTION WITHOUT BUFFER CONNECTION WITH BUFFER
LEARNING EXAMPLE
s out
V G = V GAIN
THE DETERMINE
= 0 v
+= 0
∴
=
⇒
∞
= v
+v
−v
−A
o= 0 v
−= 0
=
⇒
∞
= i
−i
+R
i0 0 0
2 1
− =
− +
R V R
V
s outv
-@ KCL APPLY
= 0 i
− 12
R R V
G V
s
out
= −
=
FOR COMPARISON, NEXT WE EXAMINE THE SAME CIRCUIT WITHOUT THE ASSUMPTION OF IDEAL OP-AMP
REPLACING OP-AMPS BY THEIR LINEAR MODEL
WE USE THIS EXAMPLE TO DEVELOP A PROCEDURE TO DETERMINE OP-AMP CIRCUITS USING THE LINEAR MODELS
1. Identify Op Amp nodes
v
−v
+v
o2. Redraw the circuit cutting out the Op Amp
v
−v
+v
o3. Draw components of linear OpAmp (on circuit of step 2)
v
−v
+v
oRi
RO
+
− A v( + −v−)
4. Redraw as needed
R
2v
−v
+INVERTING AMPLIFIER: ANALYSIS OF NON IDEAL CASE
NODE ANALYSIS
CONTROLLING VARIABLE IN TERMS OF NODE VOLTAGES
USE LINEAR ALGEBRA
Ω
= Ω
=
= 10
, 10
, 10
8
5
O
i
R
R
A : AMP -
OP
TYPICAL
1= 1 Ω ,
2= 5 Ω ⇒ = − 4 . 9996994
S O
v k v
R k
R = ∞ ⇒ = − 5 . 000
S O
v
A v
= 0 i
−= 0
=
⇒
∞
= i
−i
+R
i− +
=
⇒
∞
= v v
A
= 0 v
+= 0 v
−KCL @ INVERTING TERMINAL
0 0 0
2 1
− =
− +
R v R
v
S O1 2
R R v
v
s
O
= −
⇒
THE IDEAL OP-AMP ASSUMPTION PROVIDES EXCELLENT APPROXIMATION.
(UNLESS FORCED OTHERWISE WE WILL ALWAYS USE IT!) GAIN FOR NON-IDEAL CASE
SUMMARY COMPARISON: IDEAL OP-AMP AND NON-IDEAL CASE
NON-IDEAL CASE
REPLACE OP-AMP BY LINEAR MODEL SOLVE THE RESULTING CIRCUIT WITH DEPENDENT SOURCES
LEARNING EXAMPLE: DIFFERENTIAL AMPLIFIER
THE OP-AMP IS DEFINED BY ITS 3 NODES. HENCE IT NEEDS 3 EQUATIONS
THINK NODES!
KCL AT V_ AND V+ YIELD TWO EQUATIONS
(INFINITE INPUT RESISTANCE IMPLIES THAT i-, i+ ARE KNOWN)
OUTPUT CURRENT IS NOT KNOWN
DON’T USE KCL AT OUTPUT NODE. GET THIRD EQUATION FROM INFINITE GAIN ASSUMPTION (v+ = v-)
LEARNING EXAMPLE: DIFFERENTIAL AMPLIFIER
NODES @ INVERTING TERMINAL
NODES @ NON INVERTING TERMINAL
IDEAL OP-AMP CONDITIONS
2 4 3
4 2
4 3
0
4v
R R
v R R v
R v R
i ⇒ = +
= +
⇒
=
+ −+
−
+
=
−
+
=
− − 12 1 1
2 1
1 2 1
2
1
1 v v
R R R
v R R v R
R v
OR
) (
,
2 11 2 1
3 2
4
v v
R v R
R R
R
R = = ⇒
O= −
LEARNING EXAMPLE: USE IDEAL OP-AMP
v
O+
FIND
v
11−
v
2+
v
2−
v
1
v
o2
v
o 1v
m2
v
m6 NODE EQUATIONS + 2 IDEAL OP-AMP
2 2
1 1
v v
v v
=
=
+ +
2 2
1 1
m m
v v
v v
=
=
−
−
FINISH WITH INPUT NODE EQUATIONS…
USE INFINTE GAIN ASSUMPTION
− +
−
+
=
1 2=
21
v v v
v
2 2
1
1
v v v
v
m=
m=
∴
USE REMAINING NODE EQUATIONS
0 0 :
@
1 2 1
2 1
2 01 1
1
− + =
− +
− +
R v v
R v v
R v
v v
oG m
0 0
:
@
2 2 1
2
1 2 2
2
− + − + + =
R v R
v v
R v v v
G o
m
ONLY UNKWONS ARE OUTPUT NODE VOLTAGES VARIABLE 1
REQUIRED FOR
SOLVE vo = vo
LEARNING EXTENSION
FIND I
O. ASSUME IDEAL OP - AMP V
v
+= 12 V
v
A
O= ∞ ⇒
−= 12
= 0
⇒
∞
= i
−R
iV v
−= 12
2 0 12 12
: 12 − + =
−
k k
v V
oKCL@ ⇒ V
o= 84 V
k mA I
OV
o8 . 4
10 =
=
∴
“inverse voltage divider”
i
i
v
R R v R
R v R
v R
1 2 1
0 0
2 1
1
+
= + ⇒
=
= 0 i
−INFINITE INPUT RESISTANCE NONINVERTING AMPLIFIER - IDEAL OP-AMP LEARNING EXTENSION
v
+v
_ ov
SET VOLTAGE
v
+= v
1INFINITE GAIN ASSUMPTION
1
1 v v
v
v + = ⇒ − =
R
2R
1v
iv
−=
v 0
FIND GAIN AND INPUT RESISTANCE - NON IDEAL OP-AMP
NOW RE-DRAW CIRCUIT TO ENHANCE CLARITY. THERE ARE ONLY TWO LOOPS DETERMINE EQUIVALENT CIRCUIT USING LINEAR MODEL FOR OP-AMP
v
+v
−v
ORi
− +
R
O( )
A v
+− v
−COMPLETE EQUIVALENT FOR MESH ANALYSIS
− + v
Ov
i= v
+− v
−MESH 1
MESH 2
CONTROLLNG VARIABLE IN TERMS OF LOOP CURRENTS
) (
1 21 2
2
i R i i
R
v
O= − + −
INPUT RESISTANCE
1 1
i
R
in= v
GAINi O
v G = v
MESH 1
MESH 2
CONTROLLNG VARIABLE IN TERMS OF LOOP CURRENTS
MATHEMATICAL MODEL
) (
1 21 2
2
i R i i
R
v
O= − + −
REPLACE AND PUT IN MATRIX FORM
=
+ +
−
− +
) 0 (
)
(
12 1 2
1 1
1 2
1
v
i i R
R R
R AR
R R
R
O i
+ +
−
−
= +
−0 )
( )
(
1 12 1
1
1 2
1 2
1
v
R R
R R
AR
R R
R i
i
O i
THE FORMAL SOLUTION
) (
) )(
( R
1+ R
2+ R
OR
1+ R
2+ R
1AR
i− R
1=
∆
+
−
−
+
= +
) (
) (
) (
2 1
1
1 2
1
R R
R AR
R R
R Adj R
i
O
+
−
−
+ +
= ∆
0 ) (
) (
)
1 (
12 1
1
1 2
1 2
1
v
R R
R AR
R R
R R
i i
i
O
THE SOLUTIONS
1 2
1
1
R R R v
i
O∆ +
= +
∆
−
= − (
1)
2
R i AR
i∞ ???
→ A
1 1 2
1 1
2 1
1
2 2 1
1 1
) )(
( )
(
) (
R v AR
R v R
R R
R R
i R R
i R v
i O
O
∆
− + +
∆ +
= +
+
−
=
R
iAR
A → ∞ ⇒ ∆ →
1R
in→ ∞
1 2 1
1
R
R R
v
G = v
O→ +
A SEMI-IDEAL OP-AMP MODEL
This is an intermediate model, more accurate than the ideal op-amp model but simpler than the linear model used so far
, 0,
i O O
R = ∞ R = A = A
Non-inverting amplifier and semi-ideal model
0 i
+i
−⇒ = = v
+≠ v
−!!
Replacement Equation
( )
O O e O
v = A v = A v
+− v
−v
+v
−e in
v = v
2 1
1
(as before)
( ) (replaces )
S
O
O S O
v v
R R
v v
R
A v v v v v
+
−
− + −
=
= +
− = =
1
! 2
1 ;
O O
S O
v A R
v A β R R
⇒ = β =
+ +
actual gain-ideal gain ideal gain
GE = 1 1
A
Oβ
= +
i S
− + v
OR
+
−
+ -
v S
Sample Problem
Find the expression for Vo. Indicate where and how you are using the Ideal OpAmp assumptions
Set voltages?
v S
v + =
Use infinite gain assumption v
−= v
Sv
−Use infinite input resistance assumption and apply KCL to inverting input
= 0 + −
−R v i
Sv
oS S
o
v Ri
v = −
= 0 i
−v
+i
S− + v
OR
+
−
Sample Problem
1. Locate nodes 2. Erase Op-Amp
3. Place linear model
4. Redraw if necessary
+ -
v
ov
+v
−R
R
OR
ii
SA(v
+- v
-)
TWO LOOPS. ONE CURRENT SOURCE. USE MESHES DRAW THE LINEAR EQUIVALENT CIRCUIT AND WRITE THE LOOP EQUATIONS
i
1 2i
MESH 1
i
1= i
sMESH 2
R
i( i
2− i
S) + ( R + R
O) i
2+ A ( v
+− v
_)
CONTROLLING VARIABLE
v
+− v
_= R
i( i
2− i
1) R
i− +
R
O( )
A v
+− v
−S
= V
V
OAND GAIN
FIND
V
Sv
+=
V
Sv
_=
= 0 i
−“INVERSE VOLTAGE DIVIDER”
V
OV
S 2R
R
1 SO
V
k k V k
1 1 100 +
=
= 101
=
S O
V G V
V V
mV
V
S= 1 ⇒
O= 0 . 101
LEARNING EXTENSION
LEARNING EXAMPLE UNDER IDEAL CONDITIONS BOTH CIRCUITS SATISFY
1 2
8 4
V
O= V − V
1 2
If 1 2 , 2 3
dc supplis are 10
V V V V V V
V
≤ ≤ ≤ ≤
±
DETERMINE IF BOTH IMPLEMENTATIONS PRODUCE THE FULL RANGE FOR THE OUTPU
1 2
X
2
V = V − V
1 2
1V ≤V ≤ 2 , 2V V ≤V ≤ 3V ⇒ −1V ≤VX ≤ 2V
V
XOK!
O
4
XV = V
1 V V
X2 V 4 V V
O8 V
− ≤ ≤ ⇒ − ≤ ≤ V OK
O!
8
1V
Y= − V
1 V ≤ V
1≤ 2 V ⇒ − 16 V ≤ V
Y≤ − 8 V
EXCEEDS SUPPLY VALUE.
THIS OP-AMP SATURATES!
POOR IMPLEMENTATION
COMPARATOR CIRCUITS
Some REAL OpAmps require a “pull up resistor.”
ZERO-CROSSING DETECTOR
LEARNING BY APPLICATION
OP-AMP BASED AMMETERNON-INVERTING AMPLIFIER
1
1
2R G = + R
I R V
I=
II R R
GV R
V
O I
I
+
=
=
1
1
21
B4 (design eq.)
A
R + R =
LEARNING EXAMPLE
DC MOTOR CONTROL - REVISITEDCHOOSE NON-INVERTING AMPLIFIER (WITH POWER OP-AMP PA03)
Constraints:
V
M≤ 20 V
Power dissipation
in amplifier
≤ 100mW
Simplifying assumptions:
R
i≈ ∞ , R
O≈ ⇒ 0
Significant power losses Occur only in Ra, RbWorst case occurs when Vm=20
(20 )
2 MX100
A B
P V mW
R R
= ≤
+ ⇒ R
A+ R
B≥ 4000 Ω 3
B
A
R R =
One solution:
R
B= 3 k Ω , R
A= 1 k Ω
Standard values at 5%!
DESIGN EXAMPLE: INSTRUMENTATION AMPLIFIER
DESIGN SPECIFICATIONS
1 2
10 V
OG = V V =
−
• “HIGH INPUT RESISTENCE”
• “LOW POWER DISSIPATION”
• OPERATE FROM 2 AA BATTERIES
ANALISIS OF PROPOSED CONFIGURATION
O X Y
V = V − V
1 2 1
1
@ :V V V VX 0
A R R
− + − =
2 1 2
2
@ :V V V VY 0
B R R
− + − =
1 2 2 1
1
1
21
1 2O
R R R R
V V V V V
R R R R
= + − + + −
SIMPLIFY DESIGN BY MAKING R1 = R2 1
1 2
1 2 ( )
O
V R V V
R
⇒ = + −
DESIGN EQUATION:
2 R
1= 9 R
VO
V1
V2
G
USE LARGE RESISTORS FOR LOW POWER
e g R . ., = 100 k Ω , R
1= R
2= 450 k Ω
1
;
2A B
V = V V = V
Infinite gainMAX4240
DESIGN EXAMPLE
DESIGN SPECIFICATION O 10
in
V V =
Power loss in resistors should not exceed
100mW
2 2V Vin V
− ≤ ≤
when
Design equationS: 2
1
1 10
O
in
V R
V = + R =
1 2
2
1 2
(20 )
R R
100
P V mW
R R
+
≤ =
+
Max Vo is 20V
Solve design equations (by trial and error if necessary)
2
9
1R R
⇒ =
1 2
4
R R k
⇒ + ≥ Ω
1
400
R ≥ Ω
DESIGN EXAMPLE
IMPLEMENT THE OPERATIONV
O= − 0.9 V
1− 0.1 V
2DESIGN CONSTRAINTS
• AS FEW COMPONENTS AS POSSIBLE
• MINIMIZE POWER DISSIPATED
• USE RESISTORS NO LARGER THAN 10K Given the function (weighted sum with sign change) a basic weighted adder may work
ANALYSIS OF POSSIBLE SOLUTION
1 2
1 1 2
0
@ :
O0
V
V V V
V R R R
+
−
=
− − − =
1 21 2
O
R R
V V V
R R
⇒ = − −
2 1
2
9 0.1
R R
R R
=
=
DESIGN EQUATIONS
2 1
R > R > R
SOLVE DESIGN EQUATIONS USING TRIAL AND ERROR IF NECESSARY
2
10 ,5.6 ,...
R = k k
ANALYZE EACH SOLUTION FOR OTHER CONSTRAINTS AND FACTORS; e.g.
DO WE USE ONLY STANDARD COMPONENTS?
DESIGN EXAMPLE
DESIGN 4-20mA TO 0 – 5V CONVERTER 1. CONVERT CURRENT TO VOLTAGE USING A RESISTORI
V
I= RI
⇒
CANNOT GIVE DESIRED RANGE!
2. CHOOSE RESISTOR TO PROVIDE THE 5V CHANGE
… AND SHIFT LEVELS DOWN!
5 0
312.5 0.020 0.004
MAX MIN
MAX MIN
V V
R I I
− −
= = = Ω
− −
1.25 ≤ V
I≤ 6.25
MUST SHIFT DOWN BY 1.25V (SUBSTRACT 1.25 V)2
1 2
I
V R V
R R
+
=
+
1
1 2
(
O SHIFT)
SHIFTV R V V V
R R
−
= − +
+
( )
2
1
O I SHIFT
V R V V
= R −
V
+= V
−⇒
DOES NOT LOAD PHONOGRAPH
1000 OF
TION AMPLIFICA
AN PROVIDES IT
THAT SO
DETERMINE R
2, R
1LEARNING BY DESIGN
) 1
)(
1 (
1 2
1
R
R V
V
O= +
LEARNING EXAMPLE
UNITY GAIN BUFFER
COMPARATOR CIRCUITS
T
T
e
R = 57 . 45
−0.0227ONLY ONE LED IS ON AT ANY GIVEN TIME
MATLAB SIMULATION OF TEMPERATURE SENSOR
WE SHOW THE SEQUENCE OF MATLAB INSTRUCTIONS USED TO OBTAIN THE PLOT OF THE VOLTAGE AS FUNCTION OF THE TEMPERATURE
»T=[60:0.1:90]'; %define a column array of temperature values
» RT=57.45*exp(-0.0227*T); %model of thermistor
» RX=9.32; %computed resistance needed for voltage divider
» VT=3*RX./(RX+RT); %voltage divider equation. Notice “./” to create output array
» plot(T,VT, ‘mo’); %basic plotting instruction
» title('OUTPUT OF TEMPERATURE SENSOR'); %proper graph labeling tools
» xlabel('TEMPERATURE(DEG. FARENHEIT)')
» ylabel('VOLTS')
» legend('VOLTAGE V_T')
v
1v
+=
= 0 i
−v
1v
−=
KCL @ v_
EXAMPLE OF TRANSFER CURVE SHOWING SATURATION
THE TRANSFER CURVE
IN LINEAR RANGE THIS SOURCE CREATES THE OFFSET
OFFSET
OUTPUT CANNOT EXCEED SUPPLY (10V)